TH`ESE - Library of Ph.D. Theses | EURASIP
TH`ESE - Library of Ph.D. Theses | EURASIP TH`ESE - Library of Ph.D. Theses | EURASIP
XXII SIMPÓSIO BRASILEIRO DE TELECOMUNICAÇÕES - SBrT’05, 04-08 DE SETEMBRO DE 2005, CAMPINAS, SPthe proposed technique transforms the spatial diversity atthe BS side into time diversity at the MU side, which canbe exploited by a temporal equalizer. Our proposition thentakes into account the existent systems and only makes minorchanges to increase the diversity gain at the MU side. Theperformance of the proposed technique is however related tothe specific equalizer used at the MU. Here we assume thatthe MU uses an ideal receiver, which is capable of recoveringall the signal energy spread across time.As stated in the previous Section, at each block t a differentaverage power P t is received by the MU’s antenna. Thevariation of these received powers P t is caused by the fading.We propose thus to find a (fixed) space-time transmit filter Wthat is computed in order that the received power P t at theMU is as constant as possible over a finite training window.By doing so, we are minimizing the fading effect, i.e., thereceived power variation. This criterion can be expressed asW opt = arg minWt f∑t=t i(W H R t W − 1 ) 2(14)where t i and t f are the initial and final blocks of the trainingwindow, respectively.In order to keep the same transmit power of the singleantenna (no transmit filter) case, the optimum transmit filteris normalizedW on = W opt‖W opt ‖ . (15)This normalized optimum filter W on is then used to transmitthe subsequent data blocks. In addition, to ensure the desiredtarget SNR at the MU, a power control is done at the BS.We assume that this power control is integrated in the signals(n), i.e., this signal is already scaled in order that the receivedpower at the MU respects the target SNR.This novel criterion for transmit diversity is called ConstantPower Approach (CPA). This criterion can be optimized byusing one of the many optimization techniques existing in theliterature. In the following we propose an adaptive algorithm tooptimize the proposed criterion. It is not our goal in this workto find the best optimization technique but only to provide onetechnique in order to assess the performance of the proposedCPA.A. Obtaining W optOne can easily associate (14) with a constant modulus (CM)criterion. This criterion has been for long time investigatedand some algorithms to optimize it have been proposed inthe literature. All these algorithms are based on the followingcriterionJ CMA = arg minW∑ (W H x(n)x(n) H W − 1 ) 2. (16)nBy comparing (16) and (14), one can easily identify thecovariance matrix R t with the instantaneous signal covariancematrix x(n)x(n) H . Thus, there is a fundamental differencebetween both criteria since the CMA assumes that the matrixx(n)x(n) H has rank 1 while the matrix R t can have (andusually has) rank greater than one.Then, the already existing algorithms, such as theCMA [15], the ACMA [16] and the finite-interval constantmodulus algorithm [17], can not be directly used to optimize(14). It is our belief that these algorithms could bemodified to optimize (14). In this work, however, we proposea novel algorithm to preform this task.Based on (14), let us define the cost function to be minimizedasJ =t f∑t=t i(WHk X k (t) − 1 ) 2, (17)where X k (t) = R t W k and k is the iteration index. Thiscriterion can be easily identified as a MSE (mean squareerror) criterion. The minimization of this criterion can be doneiteratively by using the Newton’s method [18].Thus, applying the Newton’s method to (17), we obtain thatW k+1 = W k − αR −1k p k (18)where the coefficient α is taken less than 1 to avoid thedivergence of the algorithm andR k =p k =t f∑t=t iX k (t)X H k (t) =t f∑t=t iX k (t) =t f∑t f∑t=t iR t W k .t=t iR t W k W H k R H t (19a)(19b)By taking (experimentally) α = 1 4, we obtain the proposedConstant Power Algorithm (CPA):W k+1 = 1 2 W k + 1 2 R−1 k p k . (20)As we have said at the beginning of this Section, wejust present an algorithm to optimize the criterion of (14).The analytical convergence of this algorithm has not beenproved. Simulations results however indicate that the algorithmconverges. Indeed, the algorithm has never diverged in all themany cases simulated.IV. SIMULATION RESULTSWe consider the downlink of a 120 ◦ sector of a cell ofa wireless system. The data is transmitted in blocks and weassume, without loss of generality, that the channel realizationis independent from one block to another, i.e., the phases ofeach path varies from one block to another. The BS is equippedwith K antennas and, unless specified otherwise, the interelementdistance is λc2 , where λ c is the carrier wavelength.The transmit space-time filter is K × L (see Fig. 1), where Lis the number of temporal coefficients in each spatial branch.We assume that the instantaneous DCCMs R t are perfectlyknown at the BS, for all t.In order to assess the performance of the proposed technique,for each training block, a different channel was drawnand the corresponding DCCMs R t were used as input for theproposed algorithm, which computes the optimum transmitfilter W opt , see (14). The normalized optimum filter W on ,see (15), was then used to compute the received power P t atthe MU for the data blocks. With the assumption that the
XXII SIMPÓSIO BRASILEIRO DE TELECOMUNICAÇÕES - SBrT’05, 04-08 DE SETEMBRO DE 2005, CAMPINAS, SP1110K=1, L=1 (1 or 2 paths)K=2, L=1 or 2 (1 path)K=2, L=2 (2 paths)10090K=1, L=1 (1 or 2 paths)K=2, L=1 or 2 (1 path)K=2, L=2 (2 paths)Frequency [%]987654321Fig. 2.3 dB0−15 −10 −5 0 5 10 15P [dB] tHistogram of the received power P t at the MU antenna.Empirical Complementary Cumulative Distribution = Prob(BER>X) [%]807060Zoom1850161440 121030 86204210010 −4 10 −3 10 −2 10 −1 10 0010 −90 10 −80 10 −70 10 −60 10 −50 10 −40 10 −30 10 −20 10 −10 10 0BERFig. 3. Outage probability at SNR=20 dB.temporal equalizer of the MU can recover all the symbolenergy, the BER (bit error rate) at its output depends onlyon the received power P t and not on the particular equivalenttemporal channel. For each block, the theoretical BER for aQPSK modulation was calculated based on the correspondingP t and the white gaussian noise variance σ 2 at the MUantenna.We have simulated two different channels, a single pathchannel and a 2 path channel, in order to highlight the diversitygain provided by the proposed technique. In the 2 paths case,both paths have the same delay but arrives at the receiver fromtwo distinct DOAs (direction of arrival). Moreover, both pathshave the same average power of 0.5.Fig. 2 shows the histogram of the received powers P t foran SNR of 20 dB. It can be seen that for the 1 path channel,the only improvement between K=1 and K=2 is the 3 dBarray gain, i.e., only a shift to the right in the histogram(see the dotted and the dashed curves). In contrast, for the 2paths channel, the proposed technique with K=2 and L=2 canbenefit from the channel’s diversity order of 2, which can beseen by the fact that the received power is more concentratedaround its (lower) average value.Fig. 3 shows the outage probability at SNR of 20 dB, whichis the probability that the BER is above a given target BER,i.e., no reliable communication is possible. From Fig. 3, onecan see that, for the single path case, there is only a scale factorbetween the K=1 and K=2, which reflects the 3 dB array gain.However, for the 2 paths channel, the curve for K=2 and L=2(solid curve) shows that the probability of higher BERs isreduced and the BER is more concentrated at lower values,when compared to the single antenna case (dotted curve). Theoutage probability at 10 −2 are 5.122 % for K=1, 2.671 % forK=2 (one path) and 0.537 % for K=2 and L=2 (two paths).The proposed technique presents an outage probability whichis more than 9 times lower than the single antenna and almost5 times lower than the two antennas and one path channel case,which means a significant improvement in system capacity.In order to gain insight into the proposed technique, wehave simulated the 2 paths channel, with DOAs of 0 ◦ and90 ◦ , for 2 antennas (K=2) and 2 temporal coefficients (L=2).Fig. 4 shows the radiation pattern of each spatial slice (τ = 0and τ = 1). It is clear that each pattern points towards one ofthe channel’s path. Due to the delay introduced by the filter,each path will carry a different symbol. Since the symbols ofdifferent instants are independent, at the receiver’s temporalequalizer, both paths will be summed in power and a diversitygain will be obtained.In the sequel, we compare the proposed technique (CPA)with the more classical techniques of pure beamforming [19],denoted BF, and the Alamouti scheme [7]. This comparisonis carried out in an indoor environment for 3 × 10 4 blocks.The simulated indoor channel consists of a great number ofmultipaths with DOA uniformly distributed around the MUantenna. All multipaths have the same propagation delay andthus they arrive at the same instant at the MU antenna. Theoutage probability of the three techniques (when applicable)at 10 −2 is showed in Tab. I for different numbers of antennas(K) and temporal coefficients (L). It can be seen that theCPA technique have the same performance as the Alamoutischeme and pure beamforming, but is more flexible than bothtechniques since the CPA can be applied with any numberof antennas and temporal coefficients. Moreover, the CPAtechnique can be applied regardless of the correlation betweenthe antennas.Gain (dB)Gain (dB)0−5−10−15−20−100 −80 −60 −40 −20 0 20 40 60 80 100Angle0−5−10−15−20−100 −80 −60 −40 −20 0 20 40 60 80 100AngleFig. 4. Radiation patterns for each delay of the transmit filter W.τ=0τ=1
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XXII SIMPÓSIO BRASILEIRO DE TELECOMUNICAÇÕES - SBrT’05, 04-08 DE SETEMBRO DE 2005, CAMPINAS, SPthe proposed technique transforms the spatial diversity atthe BS side into time diversity at the MU side, which canbe exploited by a temporal equalizer. Our proposition thentakes into account the existent systems and only makes minorchanges to increase the diversity gain at the MU side. Theperformance <strong>of</strong> the proposed technique is however related tothe specific equalizer used at the MU. Here we assume thatthe MU uses an ideal receiver, which is capable <strong>of</strong> recoveringall the signal energy spread across time.As stated in the previous Section, at each block t a differentaverage power P t is received by the MU’s antenna. Thevariation <strong>of</strong> these received powers P t is caused by the fading.We propose thus to find a (fixed) space-time transmit filter Wthat is computed in order that the received power P t at theMU is as constant as possible over a finite training window.By doing so, we are minimizing the fading effect, i.e., thereceived power variation. This criterion can be expressed asW opt = arg minWt f∑t=t i(W H R t W − 1 ) 2(14)where t i and t f are the initial and final blocks <strong>of</strong> the trainingwindow, respectively.In order to keep the same transmit power <strong>of</strong> the singleantenna (no transmit filter) case, the optimum transmit filteris normalizedW on = W opt‖W opt ‖ . (15)This normalized optimum filter W on is then used to transmitthe subsequent data blocks. In addition, to ensure the desiredtarget SNR at the MU, a power control is done at the BS.We assume that this power control is integrated in the signals(n), i.e., this signal is already scaled in order that the receivedpower at the MU respects the target SNR.This novel criterion for transmit diversity is called ConstantPower Approach (CPA). This criterion can be optimized byusing one <strong>of</strong> the many optimization techniques existing in theliterature. In the following we propose an adaptive algorithm tooptimize the proposed criterion. It is not our goal in this workto find the best optimization technique but only to provide onetechnique in order to assess the performance <strong>of</strong> the proposedCPA.A. Obtaining W optOne can easily associate (14) with a constant modulus (CM)criterion. This criterion has been for long time investigatedand some algorithms to optimize it have been proposed inthe literature. All these algorithms are based on the followingcriterionJ CMA = arg minW∑ (W H x(n)x(n) H W − 1 ) 2. (16)nBy comparing (16) and (14), one can easily identify thecovariance matrix R t with the instantaneous signal covariancematrix x(n)x(n) H . Thus, there is a fundamental differencebetween both criteria since the CMA assumes that the matrixx(n)x(n) H has rank 1 while the matrix R t can have (andusually has) rank greater than one.Then, the already existing algorithms, such as theCMA [15], the ACMA [16] and the finite-interval constantmodulus algorithm [17], can not be directly used to optimize(14). It is our belief that these algorithms could bemodified to optimize (14). In this work, however, we proposea novel algorithm to preform this task.Based on (14), let us define the cost function to be minimizedasJ =t f∑t=t i(WHk X k (t) − 1 ) 2, (17)where X k (t) = R t W k and k is the iteration index. Thiscriterion can be easily identified as a MSE (mean squareerror) criterion. The minimization <strong>of</strong> this criterion can be doneiteratively by using the Newton’s method [18].Thus, applying the Newton’s method to (17), we obtain thatW k+1 = W k − αR −1k p k (18)where the coefficient α is taken less than 1 to avoid thedivergence <strong>of</strong> the algorithm andR k =p k =t f∑t=t iX k (t)X H k (t) =t f∑t=t iX k (t) =t f∑t f∑t=t iR t W k .t=t iR t W k W H k R H t (19a)(19b)By taking (experimentally) α = 1 4, we obtain the proposedConstant Power Algorithm (CPA):W k+1 = 1 2 W k + 1 2 R−1 k p k . (20)As we have said at the beginning <strong>of</strong> this Section, wejust present an algorithm to optimize the criterion <strong>of</strong> (14).The analytical convergence <strong>of</strong> this algorithm has not beenproved. Simulations results however indicate that the algorithmconverges. Indeed, the algorithm has never diverged in all themany cases simulated.IV. SIMULATION RESULTSWe consider the downlink <strong>of</strong> a 120 ◦ sector <strong>of</strong> a cell <strong>of</strong>a wireless system. The data is transmitted in blocks and weassume, without loss <strong>of</strong> generality, that the channel realizationis independent from one block to another, i.e., the phases <strong>of</strong>each path varies from one block to another. The BS is equippedwith K antennas and, unless specified otherwise, the interelementdistance is λc2 , where λ c is the carrier wavelength.The transmit space-time filter is K × L (see Fig. 1), where Lis the number <strong>of</strong> temporal coefficients in each spatial branch.We assume that the instantaneous DCCMs R t are perfectlyknown at the BS, for all t.In order to assess the performance <strong>of</strong> the proposed technique,for each training block, a different channel was drawnand the corresponding DCCMs R t were used as input for theproposed algorithm, which computes the optimum transmitfilter W opt , see (14). The normalized optimum filter W on ,see (15), was then used to compute the received power P t atthe MU for the data blocks. With the assumption that the