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108 Signals and Spectra Chap. 2 A = attenuation (in decibels) below the mean output power level, P = percent removed from the carrier frequency, and B = authorized bandwidth in megahertz. The FCC definition (as well as many other legal rules and regulations) is somewhat obscure, but it will be interpreted in Example 2–22. It actually defines a spectral mask. That is, the spectrum of the signal must be less than or equal to the values given by this spectral mask at all frequencies. The FCC bandwidth parameter B is not consistent with the other definitions that are listed, in the sense that it is not proportional to 1/T, the “signaling speed” of the corresponding signal [Amoroso, 1980]. Thus, the FCC bandwidth parameter B is a legal definition instead of an engineering definition. The RMS bandwidth, which is very useful in analytical problems, is defined in Chapter 6. Example 2–22 BANDWIDTHS FOR A BPSK SIGNAL A binary-phase-shift-keyed (BPSK) signal will be used to illustrate how the bandwidth is evaluated for the different definitions just given. The BPSK signal is described by s(t) = m(t) cos v c t (2–194) where v c = 2pf c , f c being the carrier frequency (hertz), and m(t) is a serial binary (;1 values) modulating waveform originating from a digital information source such as a digital computer, as illustrated in Fig. 2–23a. Let us evaluate the spectrum of s(t) for the worst case (the widest bandwidth). The worst-case (widest-bandwidth) spectrum occurs when the digital modulating waveform has transitions that occur most often. In this case m(t) would be a square wave, as shown in Fig. 2–23a. Here a binary 1 is represented by +1 V and a binary 0 by -1 V, and the signaling rate is R = 1/T b bits/s. The power spectrum of the square-wave modulation can be evaluated by using Fourier series analysis. Equations (2–126) and (2–120) give m (f) = ƒc nƒ 2 d(f-nf 0 ) = n=-q a q q a n=-q nZ0 sin(np/ 2) c np/ 2 2 d d af- n R 2 b (2–195) where f 0 = 1/12T b 2 = R/2. The PSD of s(t) can be expressed in terms of the PSD of m(t) by evaluating the autocorrelation of s(t)—that is, R s (t) = 8s(t)s(t + t)9 or = 8m(t)m(t + t) cos v c t cos v c (t + t)9 = 1 2 8m(t)m(t + t)9 cos v ct + 1 2 8m(t)m(t + t) cos (2v ct + v c t)9 R s (t) = 1 2 R m(t) cos v c t + 1 2 lim T: q 1 T L T/2 -T/2 m(t)m(t + t) cos (2v c t + v c t) dt (2–196)
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108<br />
Signals and Spectra Chap. 2<br />
A = attenuation (in decibels) below the mean output power level,<br />
P = percent removed from the carrier frequency,<br />
and<br />
B = authorized bandwidth in megahertz.<br />
The FCC definition (as well as many other legal rules and regulations) is somewhat<br />
obscure, but it will be interpreted in Example 2–22. It actually defines a spectral mask. That is,<br />
the spectrum of the signal must be less than or equal to the values given by this spectral mask<br />
at all frequencies. The FCC bandwidth parameter B is not consistent with the other definitions<br />
that are listed, in the sense that it is not proportional to 1/T, the “signaling speed” of the corresponding<br />
signal [Amoroso, 1980]. Thus, the FCC bandwidth parameter B is a legal definition<br />
instead of an engineering definition. The RMS bandwidth, which is very useful in analytical<br />
problems, is defined in Chapter 6.<br />
Example 2–22 BANDWIDTHS FOR A BPSK SIGNAL<br />
A binary-phase-shift-keyed (BPSK) signal will be used to illustrate how the bandwidth is evaluated<br />
for the different definitions just given.<br />
The BPSK signal is described by<br />
s(t) = m(t) cos v c t<br />
(2–194)<br />
where v c = 2pf c , f c being the carrier frequency (hertz), and m(t) is a serial binary (;1 values)<br />
modulating waveform originating from a digital information source such as a digital computer, as<br />
illustrated in Fig. 2–23a. Let us evaluate the spectrum of s(t) for the worst case (the widest bandwidth).<br />
The worst-case (widest-bandwidth) spectrum occurs when the digital modulating waveform<br />
has transitions that occur most often. In this case m(t) would be a square wave, as shown in<br />
Fig. 2–23a. Here a binary 1 is represented by +1 V and a binary 0 by -1 V, and the signaling rate<br />
is R = 1/T b bits/s. The power spectrum of the square-wave modulation can be evaluated by using<br />
Fourier series analysis. Equations (2–126) and (2–120) give<br />
m (f) = ƒc nƒ 2 d(f-nf 0 ) =<br />
n=-q<br />
a<br />
q<br />
q<br />
a<br />
n=-q<br />
nZ0<br />
sin(np/ 2)<br />
c<br />
np/ 2<br />
2<br />
d d af- n R 2 b<br />
(2–195)<br />
where f 0 = 1/12T b 2 = R/2. The PSD of s(t) can be expressed in terms of the PSD of m(t) by<br />
evaluating the autocorrelation of s(t)—that is,<br />
R s (t) = 8s(t)s(t + t)9<br />
or<br />
= 8m(t)m(t + t) cos v c t cos v c (t + t)9<br />
= 1 2 8m(t)m(t + t)9 cos v ct + 1 2 8m(t)m(t + t) cos (2v ct + v c t)9<br />
R s (t) = 1 2 R m(t) cos v c t + 1 2 lim<br />
T: q<br />
1<br />
T L<br />
T/2<br />
-T/2<br />
m(t)m(t + t) cos (2v c t + v c t) dt<br />
(2–196)