mohatta2015.pdf
signal processing from power amplifier operation control point of view
signal processing from power amplifier operation control point of view
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144 MAXIMUM LIKELIHOOD SEQUENCE DETECTION<br />
that need to be considered. As an example, consider M-QAM, root-Nyquist pulse<br />
shaping, and a channel consisting of two symbol-spaced paths. Suppose we first<br />
perform linear equalization. However, instead of selecting one value for each symbol,<br />
we keep the N best values, where N < M. Next we perform a reduced search<br />
Viterbi algorithm in which we only consider the N values kept for each symbol.<br />
This means we have N L ~ l states instead of M L_1 and N L branch metrics instead<br />
of M L . The parameter TV is a design parameter, allowing us to trade complexity<br />
and performance. For example, if M — 16 and N = 4, we reduce the number of<br />
states from 16 to 4 and the number of branch metrics from 256 to 16. While we<br />
have added the complexity of linear equalization, the overall complexity can still<br />
be reduced due to the reduced search.<br />
Various extensions are possible. The first equalization stage need not be linear<br />
equalization, though it should be relatively simple. Also, the first stage can actually<br />
consist of multiple sub-stages. For example, the first stage could be LE, keeping<br />
N\ < M best symbol values. The second stage could be a hybrid form (see next<br />
subsection) in which pairs of symbols are jointly detected, considering TVf combinations<br />
and keeping only N2 possible pair values, where N2 < Nf. The reduced<br />
search Viterbi algorithm would then consider symbol pairs.<br />
Multiple stages can also be used in conjunction with centrólas. In the first stage,<br />
the 16-QAM constellation is approximated as QPSK using the centroid of each<br />
quadrant. One or more centroide can be kept for further consideration. In the<br />
second stage, the centroide are expanded into the four constellation points that<br />
they represent.<br />
6.4.3.4 Sub-block forms In previous chapters, we introduced the notions of group<br />
LE and group DFE. We revisit these here, but view them from an MLSD point<br />
of view. We can interpret group LE as a form of sub-block MLSD. By modeling<br />
the symbols in the sub-block as M-ary symbols and modeling the other symbols<br />
as being Gaussian (colored noise), we obtain an approximate form of MLSD. This<br />
gives us a hybrid form that is part MLSD (joint detection of symbols within the<br />
sub-block) and part LE (linear filtering prior to joint detection). We can do the<br />
same with DFE.<br />
6.5 AN EXAMPLE<br />
GSM is a 2G cellular system [Rai91, Goo91]. GSM employs Gaussian Minimum<br />
Shift Keying (GMSK) with a certain precoding. Using [Lau86], this form of GMSK<br />
can be approximated as a form of partial response BPSK [Jun94]. Thus, even in<br />
a nondispersive channel, there is ISI due to the transmit pulse shape which spans<br />
roughly 3 symbol periods. The modem bit rate is 270.833 kbaud (symbol period 3.7<br />
/is). To handle a delay spread of up to 7.4 μβ, the equalizer needs to handle ISI from<br />
4 previous symbols. With MLSD, this leads to 16 states in the Viterbi algorithm.<br />
In [Ave89], the Ungerboeck metric is used in a 32-state Viterbi algorithm (handles<br />
more dispersion). Joint detection of cochannel interference is considered in [Che98].<br />
In [Ben94], the M-algorithm is used to reduce the complexity of a 16-state MLSD.<br />
Setting M between 4 and 6 provides performance comparable to full MLSD for the<br />
scenarios considered. The M algorithm is also used in [Jun95a].