III. Gm-C Filtering - Epublications - Université de Limoges

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Comparison of the Proposed Filters As said, a figure-of-merit has been proposed in the introduction to compare RF filters results with state-of-the art literature ones. This FOM is defined as: IIP3− NF . FOM1 moy max where TR is the frequency tuning range. 10 = 10 Q . f . TR (VI.1) It can also take into account the power consumption PDC of the filter. 10 FOM 2 = IIP3− NF . 10 Q P moy DC . f - 176 - max . TR (VI.2) Table 35 summarizes the performances obtained with the Gm-C and the Rauch filter. These two filters are compared to the most significant paper dealing with a fully active frequency tunable bandpass filter for TV tuners [VI.1]. Table 35. Performances Comparison [VI.1] Gm-C Filter 2 Rauch Filter Units Topology Gm-C (DSD) Gm-C (MGTR) Rauch - IIP3 4 9 14 dBm NF 20 16 15 dB Qmoy 6 3.7 3 - fmax 300 450 240 MHz TR = fmax/fmin 6 10 6 - Power consumption 7.6 30 155 mW Technology 130nm CMOS 65nm CMOS 0.25µm BiCMOS - Supply 1.2 2.5 3.3 V Measures / Simu. Measurements Simulations Measurements - FOM1 271 3100 3430 - FOM2 35 103 22 -
It is worth highlighting that FOM1 is the highest for the Rauch filter. Compared to the literature, the Gm-C filter designed with the MGTR technique also shows a high FOM1. Hence, this means that the Rauch filter exhibits the best RF performances versus selectivity trade-off all over the frequency tuning range. When taking into account the power consumption, the proposed Gm-C filters shows the best figure. However, process issues when implementing this solution on silicon may strongly degrade the measured results. Reference [VI.1] and the Rauch filter then present comparable FOM2 results. The Rauch filter is optimized in terms of noise and linearity whereas the filter in [VI.1] is optimized for low power consumption. Besides, it has been chosen a 3.3V supply for the Rauch to enhance the input power of the filter while keeping the specified performances. With a 1.2V supply, this input power is then reduced. Future improvements of the Gm-C would consist in working on the Gm-cell linearity versus noise trade-off. Perspectives on the Rauch filter mainly concern the improvement of the operational amplifier design in order to increase the bandwidth above 30dB voltage gain. Conclusion and Perspectives Two fully active frequency tunable bandpass filters have been simulated, and one of them measured. The results presented all along this PhD thesis open the perspective of the full integration of the silicon TV tuner over at least the first two octaves of the VHF band, leading to the emergence of the first fully-integrated silicon TV tuner. An encouraging perspective for future developments is the study of N-path filters which exhibit a wide tuning range for high RF performances and high selectivity. However, these topologies may require the modification of the front-end architecture of the tuner to be used. This may involve important changes on the specifications of each block constituting the front-end architecture to finally allow reaching targeted tuner NF and harmonic rejection for instance. Reference [VI.1] Y. Sun, C. J. Jeong, I. Y. Lee, J. S. Lee, and S. G. Lee, “A 50-300-MHz low power and high linear active RF tracking filter for digital TV tuner ICs,” presented at the Custom Integrated Circuits Conference (CICC), 2010 IEEE, 2010, pp. 1-4. - 177 -
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UNIVERSITE DE LIMOGES ECOLE DOCTORA
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Acknowledgments En préambule à ce
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Summary ACKNOWLEDGMENTS ...........
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V. A PERSPECTIVE FOR FUTURE DEVELOP
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French Introduction Les signaux TV
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I. Introduction to TV tuners and to
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I.1.b.ii Digital modulations In dig
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makes the covering of a large terri
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I.1.c.iii Terrestrial spectrum Firs
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I.1.e Broadband Reception Systems F
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I.2.b TV Tuner High Performance Spe
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I.2.b.ii High linearity Although co
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I.3 RF Filter Specifications I.3.a
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27. This leads to the downconversio
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These adjacent channel rejection re
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Above 870MHz, there are no more ter
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Newest silicon tuners generations,
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I.6 References [I.1] B. Razavi, RF
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II. Challenges of RF Selectivity Fo
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Figure 39. H3 and N+5 rejections of
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Figure 43. Second order Low-pass Fi
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Figure 46 illustrates the transfer
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H HPF s ( s) = s 1 + ω This corres
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Topologies comparison for a same Q-
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Figure 56. Low-pass to Notch Transf
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II.2 Passive LC Second Order Bandpa
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A possible solution is to split the
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II.2.c Second Order Bandpass Filter
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Figure 69. Band Switching Figure 70
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Another paper [II.7] provides a FOM
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A parallel self resonating circuit
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This gives the following values for
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Vb - 63 - M1 M2 Zin Figure 76. Anot
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when given, reported noise figures
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In all publications dedicated to Gm
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II.4.c Second Order Bandpass Filter
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Figure 87. Biquad Schematic The Gm-
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Vin Rm - 73 - C Vout Figure 89. Der
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Figure 93 depicts the RF performanc
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A second advantage of advanced BiCM
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II.7 Conclusion As a conclusion, th
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[II.13] C. Andriesei, L. Goras, and
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III.I Theoretical Study III. Gm-C F
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g V m3 in III.1.b Linearity Conside
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Assuming an ideal input transconduc
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Figure 102. Linearity of the filter
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Furthermore, a Gm-C circuit is not
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In terms of noise, the Flicker nois
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Table 7 summarizes the specificatio
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Idiff (A) levels reached with this
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III.2.e Unbalanced Differential Pai
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Hence, the combination of the expon
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Technique Current Increase Source D
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Using this structure and considerin
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The dimensioning of the transistors
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III.3.c Gm-cells with MGTR III.3.c.
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Furthermore, the high sensitivity t
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Figure 136. Filter in-band IIP3 ver
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III.4 Comparison of the filters III
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III.5 Conclusion Once the Gm-C seco
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IV. Rauch Filtering IV.1 Sallen-Key
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Thus, an equation linking Q and Gai
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IV.1.c.ii Proposed positive feedbac
Page 129 and 130: For both Rauch and Sallen-Key filte
Page 131 and 132: The high sensitivity to passive com
Page 133 and 134: Furthermore, it should also be take
Page 135 and 136: IV.2.b Innovative Implementation of
Page 137 and 138: esulting gain K, constituted of the
Page 139 and 140: Table 25. Sum-up of the OA specific
Page 141 and 142: Figure 153. OA voltage gain versus
Page 143 and 144: Filtering in the mirror, by means o
Page 145 and 146: However, this feedback makes the fi
Page 147 and 148: Figure 160. OA Gain and phase versu
Page 149 and 150: IV.3.c Implemented Filter and Test
Page 151 and 152: Figure 165 depicts the layout of th
Page 153 and 154: Figure 169. PVT variations of the f
Page 155 and 156: IV.4 Rauch Filter Performances: Mea
Page 157 and 158: Figure 178. IIP3 versus input power
Page 159 and 160: IV.4.c Performances Sum-up The filt
Page 161 and 162: Table 30. Frequency Limitations of
Page 163 and 164: IV.7 References [IV.1] Y. Tsividis
Page 165 and 166: V. A Perspective for Future Develop
Page 167 and 168: V.2 4-path Filter Simulations V.2.a
Page 169 and 170: The frequency tunability is ensured
Page 171 and 172: V.3 State-of-the-Art V.3.a 4-path F
Page 173 and 174: V.4 Conclusion In this chapter, it
Page 175 and 176: IEEE International, 2009, pp. 222-2
Page 177 and 178: RF selectivity challenges In this t
Page 179: The positive feedback Rauch filter
Page 183 and 184: étudiée. Il s’avère que la lin
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Page 187 and 188: A.3 Signal-to-Noise Ratio These dif
Page 189 and 190: A.5 Friis’ Formula In case of mul
Page 191 and 192: A.7 References [A.1] Friis, H.T., N
Page 193 and 194: To estimate the influence of the di
Page 195 and 196: Now, let’s have a look to the cub
Page 197 and 198: Figure 200. Third order intercept p
Page 199 and 200: B.2 RF Filter Linearity Measurement
Page 201 and 202: B.2.c IIP2 measurement To measure t
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Page 205 and 206: C.1 Gyrator-C filtering year Ref. f
Page 207 and 208: C.2 Gm-C Filtering year Ref. f0 (MH
Page 209 and 210: year C.3 Rm-C filtering Ref. f0 (MH
Page 211 and 212: C.5 References C.5.a Gyrator-C filt
Page 213 and 214: [C.23] J. De Lima and C. Dualibe,
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Page 217 and 218: this gives: I I I md d1 d 2 = I I =
Page 219 and 220: D.2 MOS Degenerated Common-Source C
Page 221 and 222: ⎛ I s ⎞ Vout = Vin + U T ln ⎜
Page 223 and 224: Computing, this leads to: V out + v
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Page 229 and 230: FIGURE 54. H3 AND N+5 REJECTIONS AC
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FIGURE 168. PVT VARIATIONS OF THE F
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