III. Gm-C Filtering - Epublications - Université de Limoges

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III.6 References [III.1] Y. Sun, C. J. Jeong, I. Y. Lee, J. S. Lee, and S. G. Lee, “A 50-300-MHz low power and high linear active RF tracking filter for digital TV tuner ICs,” presented at the Custom Integrated Circuits Conference (CICC), 2010 IEEE, 2010, pp. 1-4. [III.2] A.M. Niknejad, “Oscillator Phase Noise”, Integrated Circuits for Communications, University of California, Berkeley, 2009. [III.3] Willy M. C. Sansen, Analog Design Essentials. Springer, 2006. [III.4] B. Razavi, RF Microelectronics. Prentice-Hall, 1998. [III.5] G. Hau, T.B. Nishimura, and N. Iwata, « A highly efficient linearized wide-band CDMA handset power amplifier based on predistortion under various bias conditions », IEEE Transactions on Microwave Theory and Techniques, Vol. 49,pp. 1194-1201, June 2001. [III.6] S. Lou and H. Luong, “A Linearization Technique for RF Receiver Front-End Using Second-Order-Intermodulation Injection,” Solid-State Circuits, IEEE Journal of, vol. 43, 2008, pp. 2404-2412. [III.7] Y. Sun, J.-seon Lee, and S.-gug Lee, “On-chip Active RF Tracking Filter with 60dB 3rd-order Harmonic Rejection for Digital TV tuners.” 2008. [III.8] B. Gilbert, “The multi-tanh principle: a tutorial overview,” Solid-State Circuits, IEEE Journal of, vol. 33, no. 1, pp. 2-17, 1998. [III.9] K. Kimura, “The ultra-multi-tanh technique for bipolar linear transconductance amplifiers,” IEEE Transactions on Circuits and Systems I: Fundamental Theory and Applications, vol. 44, no. 4, pp. 288-302, Apr. 1997. [III.10] Tae Wook Kim and Bonkee Kim, “A 13-dB IIP3 improved low-power CMOS RF programmable gain amplifier using differential circuit transconductance linearization for various terrestrial mobile D-TV applications,” Solid-State Circuits, IEEE Journal of, vol. 41, 2006, pp. 945-953 - 118 -
IV. Rauch Filtering IV.1 Sallen-Key versus Rauch Filters IV.1.a Towards an Operational Amplifier Based Filter To circumvent the limitations of the Gm-C filters, operational amplifier based filters have been studied. Indeed it has been demonstrated that Gm-C filters are limited by strong degradation and distortions of the RF signal due to the gyrator. The idea behind using an OA based topology is to take advantage of both a high loop gain and a certain filtering of the signal at the input node VA of the active component, due to the RC network. This is illustrated in Figure 138. The final purpose is to obtain a highly linear filter not compromising the noise. Figure 138. Principle of an OA based filter Furthermore, to reduce the number of active and passive components in the circuit, it has been chosen to study a second order bandpass filter [IV.1]. As discussed in the introduction, a second order bandpass filter allows reaching the required specification on the RF filter stage. Previous literature considers two main types of second order RC bandpass filters using a single wideband amplifier: Sallen-Key filters and Rauch filters. Rauch filters are also referred as multiple feedback structures [IV.2]. Following filters are studied with two capacitors set to a common value C, as shown in Figure 139, Figure 140 and Figure 142. This simplifies computations and shows interesting properties for a frequency tunable filter as it will be detailed later. - 119 -
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UNIVERSITE DE LIMOGES ECOLE DOCTORA
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Acknowledgments En préambule à ce
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Summary ACKNOWLEDGMENTS ...........
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V. A PERSPECTIVE FOR FUTURE DEVELOP
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French Introduction Les signaux TV
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I. Introduction to TV tuners and to
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I.1.b.ii Digital modulations In dig
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makes the covering of a large terri
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I.1.c.iii Terrestrial spectrum Firs
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I.1.e Broadband Reception Systems F
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I.2.b TV Tuner High Performance Spe
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I.2.b.ii High linearity Although co
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I.3 RF Filter Specifications I.3.a
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27. This leads to the downconversio
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These adjacent channel rejection re
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Above 870MHz, there are no more ter
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Newest silicon tuners generations,
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I.6 References [I.1] B. Razavi, RF
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II. Challenges of RF Selectivity Fo
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Figure 39. H3 and N+5 rejections of
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Figure 43. Second order Low-pass Fi
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Figure 46 illustrates the transfer
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H HPF s ( s) = s 1 + ω This corres
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Topologies comparison for a same Q-
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Figure 56. Low-pass to Notch Transf
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II.2 Passive LC Second Order Bandpa
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A possible solution is to split the
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II.2.c Second Order Bandpass Filter
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Figure 69. Band Switching Figure 70
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Another paper [II.7] provides a FOM
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A parallel self resonating circuit
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This gives the following values for
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Vb - 63 - M1 M2 Zin Figure 76. Anot
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when given, reported noise figures
Page 71 and 72: In all publications dedicated to Gm
Page 73 and 74: II.4.c Second Order Bandpass Filter
Page 75 and 76: Figure 87. Biquad Schematic The Gm-
Page 77 and 78: Vin Rm - 73 - C Vout Figure 89. Der
Page 79 and 80: Figure 93 depicts the RF performanc
Page 81 and 82: A second advantage of advanced BiCM
Page 83 and 84: II.7 Conclusion As a conclusion, th
Page 85 and 86: [II.13] C. Andriesei, L. Goras, and
Page 87 and 88: III.I Theoretical Study III. Gm-C F
Page 89 and 90: g V m3 in III.1.b Linearity Conside
Page 91 and 92: Assuming an ideal input transconduc
Page 93 and 94: Figure 102. Linearity of the filter
Page 95 and 96: Furthermore, a Gm-C circuit is not
Page 97 and 98: In terms of noise, the Flicker nois
Page 99 and 100: Table 7 summarizes the specificatio
Page 101 and 102: Idiff (A) levels reached with this
Page 103 and 104: III.2.e Unbalanced Differential Pai
Page 105 and 106: Hence, the combination of the expon
Page 107 and 108: Technique Current Increase Source D
Page 109 and 110: Using this structure and considerin
Page 111 and 112: The dimensioning of the transistors
Page 113 and 114: III.3.c Gm-cells with MGTR III.3.c.
Page 115 and 116: Furthermore, the high sensitivity t
Page 117 and 118: Figure 136. Filter in-band IIP3 ver
Page 119 and 120: III.4 Comparison of the filters III
Page 121: III.5 Conclusion Once the Gm-C seco
Page 125 and 126: Thus, an equation linking Q and Gai
Page 127 and 128: IV.1.c.ii Proposed positive feedbac
Page 129 and 130: For both Rauch and Sallen-Key filte
Page 131 and 132: The high sensitivity to passive com
Page 133 and 134: Furthermore, it should also be take
Page 135 and 136: IV.2.b Innovative Implementation of
Page 137 and 138: esulting gain K, constituted of the
Page 139 and 140: Table 25. Sum-up of the OA specific
Page 141 and 142: Figure 153. OA voltage gain versus
Page 143 and 144: Filtering in the mirror, by means o
Page 145 and 146: However, this feedback makes the fi
Page 147 and 148: Figure 160. OA Gain and phase versu
Page 149 and 150: IV.3.c Implemented Filter and Test
Page 151 and 152: Figure 165 depicts the layout of th
Page 153 and 154: Figure 169. PVT variations of the f
Page 155 and 156: IV.4 Rauch Filter Performances: Mea
Page 157 and 158: Figure 178. IIP3 versus input power
Page 159 and 160: IV.4.c Performances Sum-up The filt
Page 161 and 162: Table 30. Frequency Limitations of
Page 163 and 164: IV.7 References [IV.1] Y. Tsividis
Page 165 and 166: V. A Perspective for Future Develop
Page 167 and 168: V.2 4-path Filter Simulations V.2.a
Page 169 and 170: The frequency tunability is ensured
Page 171 and 172: V.3 State-of-the-Art V.3.a 4-path F
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V.4 Conclusion In this chapter, it
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IEEE International, 2009, pp. 222-2
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RF selectivity challenges In this t
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The positive feedback Rauch filter
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It is worth highlighting that FOM1
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étudiée. Il s’avère que la lin
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It is worth noticing that S0 only d
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A.3 Signal-to-Noise Ratio These dif
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A.5 Friis’ Formula In case of mul
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A.7 References [A.1] Friis, H.T., N
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To estimate the influence of the di
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Now, let’s have a look to the cub
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Figure 200. Third order intercept p
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B.2 RF Filter Linearity Measurement
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B.2.c IIP2 measurement To measure t
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C.1 Gyrator-C filtering year Ref. f
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C.2 Gm-C Filtering year Ref. f0 (MH
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year C.3 Rm-C filtering Ref. f0 (MH
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C.5 References C.5.a Gyrator-C filt
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[C.23] J. De Lima and C. Dualibe,
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this gives: I I I md d1 d 2 = I I =
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D.2 MOS Degenerated Common-Source C
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⎛ I s ⎞ Vout = Vin + U T ln ⎜
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Computing, this leads to: V out + v
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FIGURE 54. H3 AND N+5 REJECTIONS AC
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FIGURE 168. PVT VARIATIONS OF THE F
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